6TPC150M datasheet(14/22 Pages) IRF

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March 27, 2013 | V2.2 | PD97601

IR3473

6A Highly Integrated SupIRBuck

GATE DRIVE LOGIC

The gate drive logic features adaptive dead time,

diode emulation, and a minimum lower gate interval.

An adaptive dead time prevents the simultaneous

conduction of the upper and lower MOSFETs. The lower

gate voltage must be below approximately 1V after PWM

goes HIGH before the upper MOSFET can be gated on.

Also, the differential voltage between the upper gate and

PHASE must be below approximately 1V after PWM goes

LOW before the lower MOSFET can be gated on.

The upper MOSFET is gated on after the adaptive delay

for PWM = HIGH and the lower MOSFET is gated on after

the adaptive delay for PWM = LOW. When FCCM = LOW,

the lower MOSFET is driven ‘off’ when the ZCROSS signal

indicates that the inductor current is about to reverse

direction. The ZCROSS comparator monitors the PHASE

voltage to determine when to turn off the lower MOSFET.

The lower MOSFET stays ‘off’ until the next PWM falling

edge. When the lower peak of the inductor current is

above zero, IR3473 operates in continuous conduction

mode. The continuous conduction mode can also be

selected for all load current levels by pulling FCCM to

HIGH.

Whenever the upper MOSFET is turned ‘off’, it stays

‘off’ for the Min Off Time denoted in the Electrical

Specifications. This minimum duration allows time to

recharge the bootstrap capacitor and allows the over

current monitor to sample the PHASE voltage.

COMPONENT SELECTION

Selection of components for the converter is an iterative

process which involves meeting the specifications and

tradeoffs between performance and cost. The following

sections will guide one through the process.

Inductor Selection

Inductor selection involves meeting the steady state

output ripple requirement, minimizing the switching loss

of the upper MOSFET, meeting transient response

specifications and minimizing the output capacitance.

The output voltage includes a DC voltage and a small AC

ripple component due to the low pass filter which has

incomplete attenuation of the switching harmonics.

Neglecting the inductance in series with the output

capacitor, the magnitude of the AC voltage ripple is

determined by the total inductor ripple current flowing

through the total equivalent series resistance (ESR) of the

output capacitor bank.

One can use equation 5 to find the required inductance.

ΔI is defined as shown in Figure 27. The main advantage

of small inductance is increased inductor current slew rate

during a load transient, which leads to a smaller output

capacitance requirement as discussed in the Output

Capacitor Selection section. The drawback of using smaller

inductances is increased switching power loss in the upper

MOSFET, which reduces the system efficiency and

increases the thermal dissipation.

Figure 27: Typical Input Current Waveform

Input Capacitor Selection

The main function of the input capacitor bank is to provide

the input ripple current and fast slew rate current during

the load current step up. The input capacitor bank must

have adequate ripple current carrying capability to handle

the total RMS current. Figure 27 shows a typical input

current. Equation 6 shows the RMS input current.

The RMS input current contains the DC load current and

the inductor ripple current. As shown in equation 5, the

inductor ripple current is unrelated to the load current.

The maximum RMS input current occurs at the maximum

output current. The maximum power dissipation in the

input capacitor equals the square of the maximum RMS

input current times the input capacitor’s total ESR.

The voltage rating of the input capacitor needs to be

greater than the maximum input voltage because of high

frequency ringing at the phase node. The typical

percentage is 25%.

()

(6)

ΔI

OUT

IN_RMS

⎟

⎠

⎞

⎜

⎝

⎛

⋅

∫

(

)

(5)

ΔI

OUT

⋅

−

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