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TS616 数据表(PDF) 23 Page - STMicroelectronics |
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TS616 数据表(HTML) 23 Page - STMicroelectronics |
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23 / 27 page ![]() TS616 23/27 this bias current (30 µA max.) as the 1% of the cur- rent through the resistance divider to keep a sta- ble mid-supply, two resistances of 2.2k Ω can be used in the case of a 12V power supply and two resistances of 820 Ω can be used in the case of a 5V power supply. The input provides a high pass filter with a break frequency below 10Hz which is necessary to re- move the original 0 volt DC component of the input signal, and to fix it at +VCC/2. CHANNEL SEPARATION - CROSSTALK The following figure shows the crosstalk from an amplifier to a second amplifier. This phenomenon, accentuated at high frequencies, is unavoidable and intrinsic to the circuit. Nevertheless, the PCB layout also has an effect on the crosstalk level. Capacitive coupling be- tween signal wires, distance between critical sig- nal nodes and power supply bypassing are the most significant factors. Figure 65: Crosstalk vs. Frequency AV=+4, Rfb=620Ω, VCC=±6V, Vout=2Vp CHOICE OF THE FEEDBACK CIRCUIT Table 1: Closed-Loop Gain - Feedback Compo- nents INVERTING AMPLIFIER BIASING In this case a resistance R is necessary to achieve good input biasing, see Figure 66. This resistance is calculated by assuming the neg- ative and positive input bias current. The aim is to compensate for the offset bias current which could affect the input offset voltage and the output DC component. Assuming Ib-, Ib+, Rin, Rfb and a zero volt output, the resistance R comes: R = Rin // Rfb . Figure 66: Compensation of the Input Bias Current 10k 100k 1M 10M -130 -120 -110 -100 -90 -80 -70 -60 -50 Frequency (Hz) V CC (V) Gain R fb (Ω) ±6 +1 750 +2 680 +4 620 +8 510 -1 680 -2 680 -4 620 -8 510 ±2.5 +1 1.1k +2 1k +4 910 +8 680 -1 1k -2 1k -4 910 -8 680 R Load Output Rfb Rin Ib- Ib+ Vcc+ Vcc- TS616 + _ R Load Output Rfb Rin Ib- Ib+ Vcc+ Vcc- TS616 + _ |
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