REV. 0

–16–

AD607

Table II. AD607 Gain and Manual Gain Control Voltage vs. Power Supply Voltage

Power Supply

GREF

Gain Control

Voltage

(= VMID)

Scale Factor

Scale Factor

Voltage Input Range

(V)

(V)

(dB/V)

(mV/dB)

(V)

2.7

1.35

55.56

18.00

0.360–1.800

3.0

1.5

50.00

20.00

0.400–2.000

3.5

1.75

42.86

23.33

0.467–2.333

4.0

2.0

37.50

26.67

0.533–2.667

4.5

2.25

33.33

30.00

0.600–3.000

5.0

2.5

30.00

33.33

0.667–3.333

5.5

2.75

27.27

36.67

0.733–3.667

NOTE

Maximum gain occurs for gain control voltage = 0 V.

AD607

BPF

IFOP

DMIP

VPOS

a. Biasing DMIP from Power Supply (Assumes BPF AC

Coupled Internally)

AD607

BPF

IFOP

DMIP

DMIP

b. Biasing DMIP from VMID (Assumes BPF AC Coupled

Internally)

Figure 39. Suggested Methods for Biasing Pin DMIP

For IFs < 3 MHz, the on-chip low-pass filters (2 MHz cutoff)

do not attenuate the IF or feedthrough products; thus, the maxi-

mum input voltage at DMIP must be limited to

±75 mV to al-

low sufficient headroom at the I and Q outputs for not only the

desired baseband signal but also the unattenuated higher-order

demodulation products. These products can be removed by an

external low-pass filter. In the case of IS54 applications using a

455 kHz IF and the AD7013 baseband converter, a simple

1-pole RC filter with its corner above the modulation bandwidth

is sufficient to attenuate undesired outputs.

Phase-Locked Loop

The demodulators are driven by quadrature signals that are pro-

vided by a variable frequency quadrature oscillator (VFQO),

phase locked to a reference signal applied to pin FDIN. When

this signal is at the IF, inphase and quadrature baseband out-

puts are generated at IOUT and QOUT, respectively. The

The reference signal may be provided from an external source,

in the form of a high-level clock, typically a low level signal

(

±400 mV) since there is an input amplifier between FDIN and

the loop’s phase detector. For example, the IF output itself can

be used by connecting DMIP to FDIN, which will then pro-

vide automatic carrier recover for synchronous AM detection

and take advantage of any post-IF filtering. Pin FDIN must be

The VFQO operates from 400 kHz to 12 MHz and is con-

trolled by the voltage between VPOS and FLTR. In normal op-

eration, a series RC network, forming the PLL loop filter, is

connected from FLTR to ground. The use of an integral

sample-hold system ensures that the frequency-control voltage

on pin FLTR remains held during power-down, so reacquisition

of the carrier typically occurs in 16.5

µs.

In practice, the probability of a phase mismatch at power-up is

high, so the worst-case linear settling period to full lock needs

to be considered in making filter choices. This is typically 16.5

µs

at an IF of 10.7 MHz for a

±100 mV signal at DMIP and

FDIN.

quadrature accuracy of this VFQO is typically –1.2

° at

10.7 MHz. The PLL uses a sequential-phase detector that

comprises low power emitter-coupled logic and a charge pump

(Figure 40).

SEQUENTIAL

PHASE

DETECTOR

VARIABLE-

FREQUENCY

QUADRATURE

OSCILLATOR

90

°

Q-CLOCK

(ECL OUTPUTS)

I-CLOCK

REFERENCE CARRIER

(FDIN AFTER LIMITING)

U

D

40µA

C

R

F

R

40µA

Figure 40. Simplified Schematic of the PLL and

Quadrature VCO